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**Real Time Implementation of Series Expansion Based Digital Controller for Magnetic Levitation System** ()

^{1}Department of Electrical Engineering, Motilal Nehru National Institute of Technology, Allahabad, India.

^{2}School of Electronics Engineering, Kalinga Institute of Industrial Technology, Bhubaneswar, India.

^{3}Department of Electrical Engineering, Indian Institute of Technology BHU, Varanasi, India.

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*Intelligent Control and Automation*,

**7**, 110-128. doi: 10.4236/ica.2016.74011.

1. Introduction

Magnetic Levitation technology has received tremendous innovation in various engineering fields and is being utilized in various automation applications [1] [2] . The concept behind all applications is to provide contactless levitation to reduce the effect of wear and tear, therefore, increasing the efficiency and reliability. These days, this technology has covered major applications in different areas like transportation field, maglev trains [3] [4] [5] [6] , personal rapid transit, defence area (gun, rocketry), nuclear engineering (the centrifuge of nuclear reactor), chemical engineering [7] (for analyzing foods and beverages), architectural and interior design (lamp, chair, sofa, bed, washing machine), biomedical field (heart pump) [8] [9] [10] , civil engineering [11] - [18] (magnetic bearing, elevator, lift, fan, compressor, chillers, pump and geothermal heat pumps) etc.

The magnetic levitation system is nonlinear and unstable. There are various control strategies [19] [20] available for their stable operation. Some control schemes are applied on the linearized model of magnetic levitation system and some of controllers are implemented in nonlinear environment [21] . The most common controller used is PID due to its simple construction and easy implementation. Nowadays, some extended versions of PID controllers are reported in literature such as FOPID controller [22] [23] [24] in which five tunable parameters (only three tunable parameters available in conventional PID controller) are considered and providing more flexibility for design. Fuzzy PID controller [25] [26] [27] [28] is designed with the help of expert knowledge considering the parameter uncertainties. In [28] , an Interval Type-2 Fuzzy PID control scheme is suggested for controlling of maglev system and SMC based fuzzy controller is used to minimize the effect of parameter uncertainty and disturbance [29] . In [30] , 2-DOF PID controller has been designed for magnetic levitation system to achieve the desired speed of response and tuning of PID parameters is calculated by using pole placement technique for desired damping ratio and settling time with two adjustable gains. An integral variable structure grey control [31] has been applied on SMC to overcome the chattering present in the scheme for the expected limit of uncertainties and disturbances. An adaptive robust output feedback controller [32] is designed by using backstepping approach with robustifying modification of the K-filter scheme to avoid the noise present in the sensor at the output for proper tracking of position of magnetic levitation system. H-infinity based control scheme is discussed in [33] [34] . In [34] , H∞ controller is designed to achieve the set-point regulation and disturbance attenuation. Robust dynamic sliding mode control has been designed to control the position of magnetically suspended metallic object in presence of uncertainties and nonlinear term is estimated using RENN estimator [35] [36] [37] . Fuzzy compensation based adaptive PID controller is reported in [38] in which adaptive PID is main controller and their parameters are tuned by adaptive law and Fuzzy compensation controller is designed for obtaining the guaranteed stability.

The major finding from the above existing control strategies is that, the transient response (settling time and peak overshoots) of magnetic levitation system is not up to mark. Digital control provides flexibility and easy implementation of wide range of control algorithms over there analog counter parts and also achieves deadbeat response [39] [40] [41] . Motivated from this philosophy, single loop digital controller is designed using series expansion of pulse transfer function in [42] and a modified digital controller is designed for double loop system in [43] . Gain scheduling method based digital control scheme is used to tune the parameters of power MOSFET or board impedance between each phase for optimization in current balance [44] .

Looking into the advantages of digital control, the present work proposes a control scheme for magnetic levitation system, which is based on series expansion of pulse transfer function [42] [43] that provides better transient response, fast dynamic response and also could be implemented in digital environment directly. To the best of authors’ knowledge, this digital control technique based on series expansion has not been applied so far on the maglev system. In this paper, initially non-linear maglev model is linearized, then for the linearized system, transfer function is obtained. The proposed control scheme is basically designed on the basis of number of series coefficient of plant and controller that are taken as m and n respectively. The proposed digital controller is tested for two sampling times (Ts = 0.0001 second & 0.001 second) and different combinations of series coefficients m and n for plant and controller.

2. Mathematical Modeling of Magnetic Levitation System

The systematic diagram of magnetic levitation system is shown in Figure 1 and its electrical equivalent circuit in Figure 2. This experimental setup is made by feedback instrument Ltd. [45] .

Figure 1. Magnetic levitation system.

Figure 2. Electrical circuit of magnetic levitation system.

The maglev system mainly consists of four major parts: suspended steel ball, position Infra Red (IR) sensors, controller and actuator (including electro magnet and power amplifier). The steel ball is mainly controlled through current i, as clearly indicated in Figure 2. The magnetic force acting on the steel ball depends on two parameters, first, the current i, flowing in the coil and the second one is the distance h between coil and the steel ball.

The non-linear model of magnetic levitation system [30] [45] , which relates to the current flowing in the coil i and the position h of the steel ball is expressed as:

(1)

where C is a constant value which depends on the parameters of coil, is mass of the steel ball, g is acceleration due to gravity.

The magnetic levitation system expressed by (1) is nonlinear in nature. For easy analysis and design of controller, the system is linearized about the equilibrium point (and).

(2)

The linearized model of magnetic levitation system is obtained as:

(3)

By calculating the partial derivative and taking Laplace transform on both side of Equation (3) we get the transfer function as

(4)

where and are the constant values for the maglev system and expressed as:

(5)

In electrical equivalent circuit of magnetic levitation system in Figure 2, the current i flowing in the coil is proportional to the control voltage v and expressed as:

(6)

where is the proportionality constant.

Now, the transfer function can be written as:

(7)

where is small incremental control voltage around its mean value. By considering which is the gain of (IR) sensor for conversion of position of ball in meter to voltage.

The transfer function of magnetic levitation system with sensor system is obtained as:

(8)

where is the (IR) sensor output voltage.

Using given values in the Table 1, the transfer function of the magnetic levitation system is obtained as:

(9)

The Maglev system (9) has two poles at ±46.69. It is seen that one pole lies in right half of complex s-plane so system is unstable. Hence, the aim is to design a controller, which leads to overall stable system.

3. Proposed Controller Algorithm

Let the pulse transfer function of the plant (Maglev System) and controller be P(z) and C(z) respectively [42] [43] . A unity feedback system having a digital controller is shown in Figure 3. The pulse transfer function P(z) and C(z) can be expanded in negative power of z as follows:

Table 1. The parameters of physical Maglev system [30] [45] .

Figure 3. Proposed simulation diagram.

(10)

(11)

The open loop pulse transfer function O(z) can be written as:

(12)

From (10), (11) and (12) the coefficient can be calculated in term of coefficients and as follows:

(13)

The closed loop pulse transfer function for the above system can be expanded as:

(14)

Employing (13), the coefficients are calculated using the iteration formula:

(15)

Thus, the series expansion coefficient of closed loop pulse transfer function is expressed in terms of series expansion coefficient of open loop pulse transfer function and these series coefficients are arbitraterely chosen for obtaining the desired performance. The proposed control scheme is basically design on the basis of number of series coefficient of plant (10) and number of series coefficient of controller (11) on their expansion that are taken as m and n respectively during the design procedure that are discussed in next section.

4. Controller Designing Steps

Let the pulse sequence represents desired unit pulse response. Now, we have to design a controller so that the sequence of closed loop system is approximately matched with the desired one. For designing of the controller, we have to follow the steps given:

Step 1: First specify the desired pulse response sequence and the number of series coefficient of the plant m and controller coefficients n () to be designed.

Step 2: Using the (15) solve for () with iteration formula:

(16)

Step 3: Now substitute () into (13) and construct an equation for

(17)

where

(18)

(19)

(20)

Step 4: Now, solve Equation (17) by the method of least squares and the solution of the calculated controller coefficient is obtained as:

(21)

Step 5: The controller coefficients are expressed as:

(22)

The (22) is the designed controller for a specific value of series coefficients of plant and controller as m and n respectively.

Note 1: If the response of closed loop system obtained from (22) along with (10) does not track the desired trajectory, then value of series coefficients of pant m and controller n are increased and all the above five steps are repeated.

The next section presents the simulation at different sampling times and various inputs as well as the hardware results for sinusoidal input when controller given by (22) is applied on maglev system (9).

5. Simulation and Hardware Experimental Results

The simulation diagram of proposed digital control algorithm for the controlling of maglev system is given in Figure 3.

The simulations are carried out for two cases, one at sampling time Ts = 0.0001 second and secondly at 0.001 second.

Case 1: Plots at sampling time (Ts) = 0.0001 second

Let the sampling time (Ts) is 0.0001 second and the desired pulse sequence is W = [0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1 1 1 1 1 ×××]. Now for step input we have to design a controller so that it can track the step input. Once the controller is designed with the help of series expansion of pulse transfer function subjected to step input then it is also effective for all type of inputs. The performance of designed controller depends upon number of series coefficients m and n considered for plant and controller respectively and plots are given for following conditions that are given below.

The simulation results for various combination of number of considered series coefficient of plant and controller are discussed below

1) For m = 25 & n = 2

In this case the controller series coefficient is obtained as After applying this controller on the magnetic levitation system (9), the closed loop discrete transfer function is obtained as:

(23)

The eigen values of (23) lie at 0.9911, 0.8391, 0.3362 and −0.1825 and all are within the unit circle. Hence, system is stable. The simulation results are plotted for different inputs such as step, square wave and sinusoidal in Figures 4(a)-(c).

2) For m = 25 & n = 3

In this case, the proposed controller coefficient is obtained as and the closed loop discrete transfer function is written as:

(24)

It is found that, all the eigen values of (24) lie within the unit circle. The simulation results are plotted for different inputs such as step, square wave and sinusoidal from Figures 5(a)-(c).

The step performance of proposed controller is summarized in Table 2.

Remark 1: Looking at the Table 2 for cases m = 25 & n = 2 and m = 25 & n = 3, it is seen that on increasing the number of controller coefficients n from 2 to 3, settling time

(a)(b)(c)

Figure 4. (a) Response for step input; (b) Response for square wave input; (c) Response for sinusoidal.

Table 2. Performance of proposed controller for step input (Ts = 0.0001 second).

is reduced from 0.0111 second to 0 .0057 second and overshoot is also decreased from 3.65% to 2.19%. The simulation results for various input clearly state that the proposed algorithms is gives the better tracking response whatever the input such as step, square and sinusoidal.

Note 2: Experimental results cannot be verified for sampling time Ts = 0.0001 second because the magnetic levitation provided by Feedback Instrument is manufactured for sampling time Ts = 0.001 second.

(a)(b)(c)

Figure 5. (a) Response for step input; (b) Response for square wave input; (c) Response for sinusoidal input.

Now, the performance of designed controller is tested at sampling time 0.001 second through simulation as well as on the system hardware (Magnetic Levitation System 33 - 210, Feedback Instruments) which is presented through Case 2.

Case 2: Plots at sampling time (Ts) = 0.001 second

The similar steps are carried out as in Case 1 for designing of controller. The simulation and hardware experimental results are plotted for following conditions as in Section A and Section B respectively in below.

A. Simulation results for various inputs at sampling time Ts = 0.001 second

1) For m = 7 & n = 2

In this case the controller coefficient is obtained as and with this controller the closed loop discrete transfer function for system (9) is obtained as:

(25)

and all the eigen values of (25) lie within the unit circle. The simulation results are plotted for various inputs as shown in Figures 6(a)-(c).

2) For m = 12 & n = 3

In this case the controller coefficients are obtained as . The closed loop discrete transfer for system (9) with this controller is obtained as:

(26)

Here, also all the eigen values of (26) lie within unit circle. The results are plotted for various inputs as shown in Figures 7(a)-(c).

(a)(b)(c)

Figure 6. (a) Response for step input; (b) Response for square wave input; (c) Response for sinusoidal input.

(a)(b)(c)

Figure 7. (a) Response for step input; (b) Response for square wave input; (c) Response for sinusoidal input.

Remark 2: The simulation results for Case 2 of m = 7 & n = 2 and m = 12 & n = 3 are plotted in Figures 6(a)-(c) and Figures 7(a)-(c), from the above Figures it is clear that, tracking is almost achieved for desired trajectories such as step, square and sinusoidal. The step performances for this case are summarized in Table 3.

It is seen from Table 3, the transient response (peak overshoot and settling time) has improved remarkably as the order of plant and controller coefficients are increased from m = 7 & n = 2 to m = 12 & n = 3. The experimental result has been carried in Section B.

B. Hardware experimental results

The effectiveness of proposed controller is verified on setup of maglev system (33-942S) provided by feedback instrument. The maglev setup has two PCI port as PCI1711 Lab I/O ADC port is configured for plant output and PCI1711 Lab I/O DAC port is dedicated for input to the maglev system. The maglev system is manufactured

Table 3. Performance of proposed controller for step input (Ts = 0.001 second).

for sampling time Ts = 0.001 second. The proposed hardware experimental diagram is given in Figure 8.

The hardware results are tested for all two cases as discussed in Section A for Case 2 and hardware result is plotted for sinusoidal input at sampling tine 0.001 second. The position of ball to reference input is presented in voltage [V] as well as in meter (m) along with control effort in voltage [V].

1) For m = 7 & n = 2

For this case, hardware experimental result is shown from Figure 9 for sinusoidal input.

2) For m = 12 & n = 3

For this case, the hardware experimental result is shown from Figure 10 for sinusoidal input.

Remark 3: From the hardware experimental results as shown in Figure 9(a) and Figure 9(b) and Figure 10(a) and Figure 10(b), it is noticed that the peak overshoot is less in case of m = 12 & n = 3 as compared to the when m = 7 & n = 2.

It could be remarked here that on increasing the series coefficients of plant and controller, the transient and steady state behavior of system have been improved.

Comparison

The designed control strategy is quite useful for complex system and it can be easily implemented on any real time system via computer-programmed algorithm where as conventional continuous control scheme may suffer during real time implementation of linear or nonlinear control algorithms. To show the effectiveness of proposed control strategy, a comparative simulation result of designed control scheme (m = 25 & n = 3 at sampling time 0.0001 second) with conventional PID () and FOPID () control scheme for the considered maglev system (9) are shown in Figure 11.

The comparative results analysis with conventional PID and FOPID controller are given in Table 4.

From the Figure 11, it is clear that the designed controller is performed well and ball of maglev system tracks more accurately to the reference trajectory. The system performances are improved, which are clearly listed in Table 4. The performance designed controller is also depend on sampling time of specified system that are also noticed via the Table 2 and Table 3 where system performances are subsequently improved by increasing the sapling time and series coefficients of plant and controller. Due to hardware limitation, the experimental results are carried out for sampling time Ts = 0.001 second only and cannot be verified for sampling time Ts = 0.0001 second because the

Figure 8. Hardware experimental diagram.

(a)(b)

Figure 9. (a) Response for sinusoidal input (hardware); (b) Desired & ball position (m) and Control effort [V] for sinusoidal input (hardware).

(a)(b)

Figure 10. (a) Response for sinusoidal input (hardware); (b) Desired & ball position (m) and Control effort [V] for sinusoidal input (hardware).

Figure 11. Desired and ball position (comparative).

magnetic levitation provided by Feedback Instrument is manufactured for sampling time Ts = 0.001 second.

The designed controller lies in z-domain and it will bypass the requirement of higher sampling rate. Another beauty of this design algorithm is that it is applicable to any higher order system also.

Table 4. Comparative result of proposed control, PID and FOPID control strategy.

6. Conclusion

An algorithm for digital controller design has been proposed and implemented for a magnetic levitation system. The proposed digital controller is designed based on series expansion of pulse transfer function by solving a linear equation using the method of least squares. The simulation and hardware experimental results are given to show the applicability of proposed controller. The designed controller provides better tracking and transient response (settling time and peak overshoots etc.) as number of series coefficient of plant and controller is increased. The designed algorithm used for the control input is not iterative so the calculation is very fast. The proposed control technique is also compared with convention PID and FOPID control scheme. In this method the reliability criterion for a controller should be satisfied when the desired pulse response sequence is known. This method can be used for stable plant as well as unstable plant. Furthermore, it is possible to extend the method for multi input multi output (MIMO) system also.

Conflicts of Interest

The authors declare no conflicts of interest.

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